Low loss bridge electrode with rounded corners for electro-optic modulators

ABSTRACT

An electro-optic modulator having a substrate, one or more optical waveguides, at least one active electrode formed on the substrate and aligned over the optical waveguide, the active electrode operating to induce a refractive index change in the optical waveguide. The active electrode has a lower surface arranged facing the substrate, an upper surface arranged away from the substrate, substantially planar side walls, and rounded corners between the side walls and the lower surface of the active electrode. The electrode can be a bridge electrode, with two lower portions and an upper portion connected to the lower portions, the lower portions spaced apart from each other, each of the two lower portions of the active electrode extending over one of the optical waveguides. Each of the lower portions has rounded convex corners. The upper surface of the electrode can also have rounded corners or a completely rounded upper surface.

BACKGROUND

1. Field of the Invention

This application is related to electro-optic modulators and electrodes for use in electro-optic modulators.

2. Description of Related Art

Electrooptic devices, such as optical modulators, have the ability to change a particular characteristic of an optical signal, such as its intensity, phase, or polarization. Electro-optic modulators, particularly lithium niobate (LiNbO₃) modulators, have application in radio frequency analog links, digital communications and electric field sensing. Electro-optic modulators are useful for modulating an optical signal in a waveguide with an RF or other frequency electrical signal.

A variety of electro-optic modulators are disclosed in Wooten, E. L, Kissa, K. M., Yi-Yan, A., Murphy, E. J., Lafaw, D. A., Hallemeier, P. F., Maack, D., Attanasio, D. V., Fritz, D. J., McBrien, G. J., Bossi, D. E., “A review of Lithium Niobate Modulators for Fiber-Optic Communications Systems,” IEEE Journal of Selected Topics in Quantum Mechanics, Vol. 6, No. 1, 2000.

Electro-optic modulators formed in x-cut and z-cut lithium niobate are disclosed in U.S. Pat. No. 5,416,859 to Burns et al., U.S. Pat. No. 6,016,198 to Burns et al., U.S. Pat. No. 6,304,685 to Burns, U.S. Patent Application Publication No. 2004/0061918 A1, U.S. Patent Application Publication No. 2004/0095628 A1, U.S. Patent Application Publication No. 2004/0136634 A1, U.S. Patent Application Publication No. 2004/0151414 A1, U.S. Pat. No. 5,388,170, U.S. Pat. No. 5,712,935, U.S. Pat. No. 6,522,793, U.S. Pat. No. 6,600,843, U.S. Patent Application Publication No. 2004/0114845 A1, U.S. Pat. No. 5,153,930, U.S. Pat. No. 5,189,713, U.S. Pat. No. 5,953,466, U.S. Pat. No. 6,501,867, U.S. Patent Application Publication No. 2004/0066549, U.S. Patent Application Publication No. 2004/0145797, and U.S. Patent Application Publication No. 2003/0228081. Electro-optic devices with a lithium niobate substrate are also disclosed in U.S. Patent Application Publication No. 2004/0202395, U.S. Patent Application Publication No. 2004/0240036, U.S. Patent Application Publication No. 2004/0240790, U.S. Patent Application Publication No. 2004/0247220, U.S. Patent Application Publication No. 2004/0264832, U.S. Pat. No. 5,442,719, U.S. Pat. No. 5,497,233, U.S. Pat. No. 6,128,424, and U.S. Patent Application Publication No. 2004/0067021.

Reflection traveling-wave interferometric modulators are disclosed in W. K. Burns, M. M. Howerton, R. P. Moeller, R. W. McElhanon, A. S. Greenblatt, “Broadband reflection traveling-wave LiNbO3 modulator”, OFC '98 Technical Digest, 1998, pp. 284-285, and in W. K. Burns, M. M. Howerton, R. P. Moeller, R. W. McElhanon, A. S. Greenblatt, “Reflection Traveling Wave LiNbO3 Modulator for Low Vπ Operation,” LEOS 1997, IEEE p 60-61, and in W. K. Burns, M. M. Howerton, R. P. Moeller, A. S. Greenblatt, R. W. McElhanon, “Broad-Band Reflection Traveling-Wave LiNbO3 Modulator,” IEEE Photonic Technology Letters, Vol. 10, No. 6, June 1998, pp. 805-806.

Mach-Zehnder traveling-wave electro-optic modulators with waveguides formed in a z-cut lithium niobate substrate are disclosed in W. K. Burns, M. M. Howerton, R. P. Moeller, R. Krahenbuhl, R. W. McElhanon, and A. S. Greenblatt, “Low-Drive Voltage, Broad-Band LiNbO₃ Modulators with and Without Etched Ridges,” Journal of Lightwave Technology, Vol. 17, No. 12, December 1999, pp. 2551-2555 and in M. M. Howerton, R. P. Moeller, A. S. Greenblatt, and R. Krahenbuhl, “Fully Packaged, Broad-band LiNbO₃ Modulator with Low Drive Voltage”, IEEE Photonics Technology Letters, Vol. 12, No. 7, July 2000, pp. 792-794. A 40 Gb/s Mach-Zehnder modulator with traveling wave electrode is disclosed in M. Sugiyama, M. Doi, S. Taniguchi, T. Nakazawa, and H. Onaka, “Driver-less 40 Gb/s LiNbO₃ Modulator with Sub-1 V Drive Voltage”, OFC 2002, FB6-2-FB6-4.

Integrated optical photonic RF phase shifters are disclosed in E. Voges, K. Kuckelhaus, and B. Hosselbarth, “True time delay integrated optical RF phase shifters in lithium niobate”, Electronics Letters, Vol. 33, No. 23, 1997, pp. 1950-1951.

Waveguide horns for use in electro-optic modulators are disclosed in U.S. Pat. No. 6,356,673 to Burns et al. Electrodes suitable for use in electro-optic modulators are disclosed in U.S. Pat. No. 6,381,379 to Burns et al. Additional electro-optic modulators are disclosed in U.S. Pat. No. 6,393,166 to Burns, U.S. Pat. No. 6,526,186 to Burns, and U.S. Pat. No. 6,535,320 to Burns.

Lithium-tantalate based electro-optic modulators are discussed in W. K. Burns, M. M. Howerton, and R. P. Moeller, “Performance and Modeling of Proton Exchanged LiTaO3 Branching Modulators”, Journal of Lightwave Technology, Vol. 10, No. 10, October 1992, pp. 1403-1408.

Multiple-pass reflective electro-optic modulators are disclosed in commonly assigned patent application Ser. No. 10/165,940, now issued as U.S. Pat. No. 6,862,387, incorporated by reference in its entirety, and in M. M. Howerton, R. P. Moeller, and J. H. Cole, “Subvolt Broadband Lithium Niobate Modulators” 2002 NRL Review, pp 177-178. The low-loss compact turns increase the active length of a modulator and achieve a reduction in drive voltage Vπ without sacrificing a great deal of space on the substrate material.

Electrodes for use in lithium niobate modulators are also discussed in R. Krahenbuhl and M. M. Howerton, “Investigations on Short-Path-Length High-Speed Optical Modulators in LiNbO₃ with Resonant-Type Electrodes”, Journal of Lightwave Technology, Vol. 19, No. 9, September 2001, pp. 1287-1297.

Mach Zehnder interferometers with etched ridges between the electrodes and waveguides are disclosed in W. K. Burns, M. M. Howerton, R. P. Moeller, R. W. McElhanon, and A. S. Greenblatt, “Low Drive Voltage, 40 GHz LiNbO₃ Modulators”, OFC '99, pp 284-286.

BRIEF SUMMARY OF EMBODIMENTS OF THE INVENTION

An embodiment of the invention is directed to an electro-optic modulator having a substrate having at least one optical waveguide formed on a face of the substrate and at least one active electrode formed on the first face of the substrate and aligned over the optical waveguide. The active electrode operates to induce a refractive index change in the optical waveguide. The active electrode has a lower surface arranged facing the substrate, an upper surface arranged away from the substrate, and substantially planar side walls extending between the lower and upper surfaces. The active electrode has rounded corners between the side walls and the lower surface of the active electrode.

Another embodiment of the invention is directed to an electro-optic modulator having a substrate having at least one optical waveguide formed on a face of the substrate, and at least one active electrode formed on the first face of the substrate aligned over the optical waveguide and operable to induce a refractive index change in the optical waveguide. The active electrode has a wider portion and at least two narrower portions, with the narrower portions arranged between the wider portion and the optical waveguide. The narrower portions have a surface arranged facing the substrate, the wider portion having an upper surface arranged away from the substrate, and substantially planar side walls extending between the lower and upper surfaces of the electrode. The active electrode has rounded corners between the side walls and the lower surface of the active electrode.

A more complete appreciation of the invention will be readily obtained by reference to the following example embodiments and the accompanying drawings.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a plan view of an electro-optic modulator according to a first embodiment of the invention.

FIG. 2 is a cross-sectional view of the modulator of FIG. 1 at line A-A.

FIG. 3 is a cross sectional view of an electro-optic modulator according to a second embodiment of the invention.

FIG. 4 is a cross-sectional view of the modulator of FIG. 3 in an active region at line B-B.

FIG. 5 illustrates a view of the electrodes in the bend region corresponding to FIGS. 3 and 4.

FIG. 6 is a graph illustrating projected drive voltage versus frequency for bridge electrodes according to embodiments of the invention.

FIG. 7 is of electrode transmission versus frequency for coplanar waveguides and for bridge electrodes in accordance with an embodiment of the invention.

FIG. 8 illustrates the electrode loss versus electrode gap for coplanar waveguide structures.

FIG. 9 illustrates the projected drive voltage versus frequency for coplanar waveguide structures.

FIG. 10 illustrates the loss coefficient, dc drive voltage Vπ (DC) and 20 GHz drive voltage Vπ (20 GHz) for coplanar waveguide structures.

FIG. 11 is an expanded view of the bridge electrode according to FIG. 2 or 4.

FIG. 12 illustrates a lower level of a bridge electrode according to an embodiment of the invention.

FIG. 13A-B are cross sectional views of an electro-optic phase modulator according to an embodiment of the invention.

FIG. 14 is a cross sectional view of an electrode in accordance with another embodiment of the invention.

FIG. 15 is a cross sectional view of an electrode in accordance with another embodiment of the invention.

FIG. 16A-16M illustrate steps in an exemplary method for forming an electrode in accordance with an embodiment of the invention.

FIG. 17 illustrates another electro-optic modulator in according with an embodiment of the invention.

DETAILED DESCRIPTION OF THE INVENTION

When configured as MZMs, the electro-optic modulators and electrode structures described herein are useful for amplitude modulation of optical signals. The electrode structures described herein are also suitable for electro-optic phase modulators.

A waveguide is formed of a substrate material and a conveying medium. The substrate can be made of any suitable material, including ferroelectric materials such as lithium niobate, suitable for titanium diffused or proton exchange waveguides; lithium tantalate (LiTaO₃), which is typically used with proton exchange waveguides; barium titanate (BaTiO₃); strontium barium niobate (SrBaNbO₃); various polymers; and semiconductor materials such as indium gallium arsenide phosphide (InGaAsP), indium phosphide (InP), gallium arsenide (GaAs), and gallium aluminum arsenide (GaAlAs). The conveying medium can be any suitable material which has a higher refractive index than the substrate after formation of the optical waveguide. Since lithium niobate has good long term stability, low optical loss, a strong electro-optic coefficient, and the ability to operate at high frequencies, the description that follows will be made in the context of titanium-diffused waveguides in lithium niobate substrates, although it should be understood that other materials can be used.

An embodiment of the invention herein provides an electro-optic device, and specifically, a Mach-Zehnder modulator with an extremely low-loss electrode. The low-loss electrodes described herein are desired for high frequency applications and allow the incorporation of recently developed low-loss, integrated compact turns described in U.S. Pat. No. 6,862,387, suitable for interconnecting multiple devices or regions on the same chip, increasing the device active length, and increasing the device density. Compact turns in an integrated optic modulator allows an increase in the active length of the modulator without sacrificing a great deal of space on the substrate material. The drive voltage at dc is inversely proportional to the device length. Accordingly, compact turns also provide a means for achieving a desirable reduction in drive voltage.

Several embodiments of low-loss electrodes are disclosed in U.S. Pat. No. 7,224,869 and U.S. Patent Publication No. US 2007-0165977 A1, and provisional application No. 60/556,012, filed on Mar. 12, 2004. The entire disclosures of these documents are incorporated by reference herein. The “bridge” configuration electrode structures disclosed in these documents are useful in electro-optic devices with long active lengths, since an increase in active length increases the overall electrode loss.

FIG. 1 illustrates a single pass electro-optic Mach-Zehnder modulator 100 in accordance with an exemplary embodiment of the invention. The modulator includes optical waveguides formed in a substrate and electrodes arranged to induce index changes in the optical waveguides. A single hot input electrode receives a RF signal from a coplanar waveguide input horn. The base layer of the hot input electrode is split into two electrodes that are approximately the same width as the two optical waveguide arms of the modulator. A wider upper portion of the hot electrode electrically connects the lower electrode portions. The RF input signal in the electrode portions overlying the optical waveguide arms induces index changes in the optical waveguides arms. The electrode is designed such that the velocity of the RF signal traveling down the electrodes matches, as closely as possible, the velocity of the optical wave traveling within the waveguide under the electrode. One of the optical waveguide arms is reverse poled relative to the other waveguide arm. Thus, the in-phase RF input signal traveling through the electrode induces opposite phase shifts in the optical waveguide arms. Further details are provided in the following paragraphs. Note that FIG. 1-5 are not to scale.

In the exemplary embodiment shown in FIGS. 1 and 2, the substrate 160 is z-cut lithium niobate, and the optical waveguide channels 140 and 142 are formed by high temperature indiffusion of a titanium that has been photolithographically defined.

The optical waveguides are formed in a pattern such that an input waveguide 132 is split at a y-branch 136 into two parallel waveguides 140 and 142, which are then recombined into a single output waveguide 134 by an output y-branch 138. In an alternative embodiment (not shown), each of the parallel waveguides 140 and 142 can be coherently combined using a directional coupler providing two separate outputs from the device, without the output y-branch 138 and output waveguide 130.

As seen in FIG. 2, a buffer layer 170 can be arranged between the z-cut lithium niobate substrate 160 and the electrodes 110, 120, and 150 at least in the areas that will underlie the electrodes. The buffer layer 170 can be silicon dioxide or other suitable material. If the substrate is x-cut lithium niobate, no buffer layer is necessary provided that the electrodes are beside the waveguides rather than on top of them. In another embodiment (not shown), the buffer layer 170 can also be disposed over the substrate 160 in the regions between the electrodes.

As illustrated in FIGS. 1 and 2, the ground electrodes 110 and 120 are arranged on either side of and spaced apart from the central active electrode 150. Details of suitable materials and suitable techniques for diffusing titanium into the substrate are found in commonly assigned U.S. Pat. No. 6,862,387.

A cross-sectional view of the active electrode is shown in FIG. 2, corresponding to the central linear active portion of the modulator between the turns. The active or hot electrode 150 is arranged over both of the parallel waveguides 140 and 142. The hot electrode 150 has a bridge configuration, with two lower portions 152 and 154 aligned preferably directly over the parallel waveguides 140 and 142. The hot electrode's lower portions 152 and 154 are approximately the same width as the parallel waveguides 140 and 142. The lower portions of the electrode 150 are separated by a distance that is approximately the same width as the distance between the optical waveguide channels 140 and 142. The space 162 can be empty (e.g., filled with air) or can be filled with an electrically insulating material preferably with a low dielectric constant.

The upper portion 156 of the bridge-shaped hot electrode 150 has a width approximately the same as the optical waveguides 140 and 142 plus the distance between the optical waveguides, and is aligned over and in physical contact with the lower portions of the electrode.

FIG. 1 shows the electrode 150 with the upper portion 156 cut away to illustrate the alignment of the electrode legs or lower portions 152 and 154 over the optical waveguide arms 140 and 142. In the region 144 where the optical waveguide arms are approximately linear and parallel, the lower parts of the electrode 150 are aligned over the optical waveguide arms.

The active electrode and ground electrodes are configured to match as closely as possible the velocity of the RF signal in the active electrode 150 and the velocity of the optical signal in the optical waveguide channels 140 and 142. For example, the overall width of the active electrode is not limited to the width of the optical waveguide, as in some conventional MZMs, but may be equal to the sum of the widths of the optical waveguides plus the edge-to-edge separation distance between the two optical waveguides. The larger size of the bridge electrode allows much wider gap spacing between the active center electrode 150 and the ground electrodes 110 and 120 than in conventional MZM designs. The wider gap spacing allows the electrodes to be made much thicker (in the z direction of FIG. 2), resulting in considerably lower electrical losses in the electrodes.

At either end of the active region 144, the two electrode legs 152, 154 that form the base of the electrode bridge 150 are recombined and preferably terminated with a resistor equal to the characteristic impedance of the transmission line. For an unamplified input signal, this configuration approximately provides an additional 2^(1/2) direct improvement over an electro-optic modulator with one hot electrode over one waveguide and a ground plane over the waveguide and an equivalent active modulation length.

In the exemplary embodiment of FIG. 1-2, an optical source such as a laser (not shown) provides optical energy into the optical waveguide input 132. The device of FIG. 1-2 is configured to receive optical energy at the 1.5 micron wavelength, however, optical energy at other wavelengths is also suitable. For example, optical energy at the 1.3 micron wavelength can be carried by the optical waveguide 132. The dimensions of the optical waveguide can also be adjusted to carry optical energy at longer or shorter wavelengths.

Another exemplary embodiment of an electro-optic modulator is illustrated in FIG. 3-5.

FIG. 3 illustrates a multiple-pass electro-optic Mach-Zehnder modulator 300 in accordance with another exemplary embodiment of the invention. The modulator 300 includes optical waveguides formed in a substrate and electrodes arranged to induce index changes in the optical waveguides. A single hot input electrode 350 receives a RF signal from a coplanar waveguide input horn.

The base layer of the hot input electrode 350 is split into two electrodes that pass over two optical waveguide arms of the modulator. The RF input signal induces index changes in the optical waveguides modulating the velocity of the propagating optical signals. One of the optical waveguide arms is reverse poled relative to the other waveguide arm. Thus, the in-phase RF input signal traveling through the electrodes induces opposite phase shifts in the optical waveguides. The electrode is designed such that the velocity of the RF signal traveling down the electrodes matches, as closely as possible, the velocity of the optical wave traveling within the waveguide under the electrode. Further details are provided in the following paragraphs.

As illustrated in FIG. 3, the active region is folded back and forth in order to increase the interaction length, resulting in a reduced drive voltage. The modulator 300 includes a long active modulation region 380 with five approximately linear portions in which the active electrode overlies the waveguide arms. Compact reflective waveguide turns 382 are provided at the ends of the linear portions, as disclosed in U.S. Pat. No. 6,862,387 and discussed in the following paragraphs.

The optical waveguides are formed in a pattern such that an input waveguide 332 is split at a y-branch 336 into two parallel waveguide channels 340 and 342. At the end of the optical waveguide opposite the input portion 332, the optical waveguide channels 340 and 342 each include a compact 180 degree waveguide s-bend turn. As illustrated in FIG. 3, the modulator 300 includes reflective surfaces 381 and 383 at the edges of the substrate 360 adjacent the optical waveguide turns 382. The reflective surfaces can be gold or dielectric mirrors, or any other suitable material with a high reflectivity at the wavelength of the optical energy carried by the optical waveguides.

As discussed in U.S. Pat. No. 6,862,387, reflective surfaces 381 and 383 can be formed on an edge of the substrate 360 which should be polished to a smooth surface before application of the reflective surface. Smoothness of the substrate edge in the vicinity of the optical waveguides should be about or better than ⅕ of the typical wavelength of 1.5 microns or about 0.3 microns. Waveguide portions 340 a and 340 b, for example, meet at an apex 343. As discussed in U.S. Pat. No. 6,862,387, the distance of the apex of the optical waveguide to the reflecting surface 381 in the y direction can be between 0 and plus or minus 14 microns. The optical waveguides 340 and 342 can be between about 50 to 500 microns apart, measured from the centerline of the optical waveguides, and should be sufficient to limit coupling via the evanescent wave effect between waveguide arms. The reflective surface 381 is not exactly at 90 degrees to the incoming light in the optical waveguide arms. The offset from 90 degrees can be below about 10 degrees, providing a compact modulator with more than one pass and therefore a longer active region. Reflective surfaces can also be formed by etching a groove in the substrate, and depositing a material that is highly reflective at the optical frequency, as discussed in U.S. Pat. No. 6,862,387.

Reflective surfaces can also be formed by etching a groove in the substrate, and making use of total internal reflection if the incident angle is sufficiently large.

Light in the optical waveguide arm 340 a will propagate along the lower s-bend half and will be reflected by reflective surface 381, proceeding along the upper s-bend half to the optical waveguide arm 340 b. Similarly, light in the optical waveguide arm 342 a will propagate along the lower s-bend half and will be reflected by reflective surface 381, proceeding along the upper s-bend half to the optical waveguide arm 342 b. After being reflected by the reflecting surfaces and modulated in the active regions 380 between the compact s-bend turns, the signals in the optical waveguide arms will be recombined at the output y-branch 338 and will exit the modulator through output waveguide 334. In an alternative embodiment (not shown), each of the parallel waveguides 340 and 342 can be coherently combined using a directional coupler providing two separate outputs from the device, without the output y-branch 338 and output waveguide 334.

In the active regions 380 of the modulator, the optical waveguide arms 340 and 342 follow the path of the electrodes 310, 320, and 350. Compact reflective waveguide turns in the bending regions allow compact spacing of the adjacent active regions in the x-direction. In alternative embodiment (not shown), the optical waveguides can follow a semicircular path in the bending regions, however, this would require several times more space to contain the same number of active regions or transition to a high index gradient waveguide.

The substrate 360 is preferably formed of a crystalline material having a high electro-optic coefficient such as lithium niobate or lithium tantalate. Other suitable materials include barium titanate, strontium barium niobate, a polymer, indium gallium arsenide phosphide, indium phosphide, gallium arsenide, and gallium aluminum arsenide. In the exemplary embodiment shown in FIGS. 3 and 4, the substrate 360 is z-cut lithium niobate, and the optical waveguide channels 340 and 342 are formed by high temperature indiffusion of a titanium that has been photolithographically defined.

As illustrated in FIGS. 3 and 4, the ground electrodes 310 and 320 are arranged on either side of and spaced apart from the centrally arranged hot or active electrode 350. A cross-sectional view of the active electrode 350 is shown in FIG. 4, corresponding to the central linear active portion of the modulator between the turns. The active or hot electrode 350 is arranged over both of the parallel waveguides 340 and 342. The hot electrode 350 has a bridge configuration, with two lower portions 352 and 354 aligned preferably directly over the parallel waveguides 340 and 342 in the linear portions of the active region. As illustrated in FIG. 4, the hot electrode's lower portions 352 and 354 are approximately the same width as the parallel waveguides 340 and 342. The lower portions of the electrode 350 are separated by a distance that is approximately the same width as the distance between the optical waveguide channels 340 and 342. The space 362 can be empty (e.g., filled with air) or can be filled with an electrically insulating material preferably with a low electro-optic coefficient.

As illustrated in FIG. 4, the upper portion 356 of the bridge-shaped hot electrode 350 has a width approximately the same as the optical waveguides 340 and 342 plus the distance between the optical waveguides, and is aligned over and in physical contact with the legs or lower portions of the electrode. The electrode can be formed in two or more steps, with a base layer being deposited first to form the lower electrode portions, and the upper portion of the electrode being formed of subsequently applied layer or layers of metallization. The upper portion 356 of the hot electrode 350 can have a width approximately equal to the widths of the electrode legs plus the gap between the legs, as seen in FIG. 4. The upper portion must be in electrical contact with the electrode base portions, although it is not necessary that the upper portion of the electrode be precisely aligned over the electrode base portions. The width of the upper portion can be slightly less than the widths of the electrode legs plus the gap between the legs. The width of the upper portion can also be greater than the widths of the electrode legs plus the gap between the legs, as seen in the electrode embodiments illustrated in FIG. 13A-B.

FIG. 3 shows the electrode 350 with the upper portion 356 cut away to illustrate the alignment of the electrode legs or lower portions 352 and 354 extending over and aligned with the optical waveguide arms 340 and 342 in the parts of the active region 380 where the optical waveguides are approximately linear and parallel.

A buffer layer 370 can be arranged between the z-cut lithium niobate substrate 360 and the electrodes 310, 320, and 350 at least in the areas that will underlie the electrodes. The buffer layer 370 can be silicon dioxide or other suitable material. If the substrate is x-cut lithium niobate, no buffer layer is necessary. The buffer layer 370 can also be disposed over the substrate 360 in the regions between the electrodes.

The electrode structure may be terminated with a resistor with the characteristic impedance of the transmission line.

The active electrode and ground electrodes are configured to match as closely as possible the velocity of the RF signal in the active electrode 350 and the velocity of the optical signal in the optical waveguide channels 340 and 342 in the linear region between the turns. For example, the overall width of the active electrode is not limited to the width of the optical waveguide, as in some conventional MZMs, but can be equal to about twice the width of the a waveguide plus the edge-to-edge separation between the two waveguides, or greater. The larger size of the bridge electrode allows much wider gap spacing between the active center electrode 350 and the ground electrodes 310 and 320. The wider gap spacing allows the electrodes to be made much thicker (in the z direction), resulting in lower electrical losses in the electrodes.

The surface of the substrate 360 can be removed by etching or other suitable removal technique in the gaps between each ground electrode 310, 320 and the hot electrode 350. The substrate surface can also be removed in the space 362 between the two lower portions of the active electrode 350. FIG. 4 illustrates that in the linear part of the active region of the modulator, the upper surface of the lithium niobate substrate 360 has been removed by etching in the space 362 between the active electrode legs 352, 354 and in the region 364, 366 between the ground electrodes 310, 320 and the active electrode 350. Removing a portion of the substrate appears to improve the velocity matching between the RF and optical signals by increasing the velocity of the RF signal in the active electrode. Removal of a portion of the substrate also can affect the impedance of the electrode. The bridge electrode, when optimized to match the RF and optical velocities, has a characteristic impedance lower than 50 ohms without etching.

Etching the substrate surface in the bend regions is difficult to accomplish without damaging the optical waveguide crossings near the reflective s-bends. To impedance match the bridge electrode in the turning region, the height of the electrode is reduced to a height less than the height in the linear active region to obtain 50 ohms without etching the lithium niobate substrate. For example, when the bridge electrode height is 90 microns in the linear part of the modulator, the bridge electrode height in the turning region is 30 microns thick. The reduced height of the electrodes in the bending region, however, can cause a mismatch between the velocities of the RF and optical signals. Therefore, the physical lengths of the optical waveguides and the electrodes are selected to match the total transit time of the optical and electrical signals through the bend region, ensuring they are in phase as they transition through the turn into the next linear active region. A three dimensional electromagnetic model can be used to determine the appropriate lengths of the optical waveguides and electrodes in the bend region and linear active regions. FIG. 5 illustrates the bridge electrode 350 and the ground electrodes 310 and 320 in the turning region of the modulator.

The side walls of the electrodes can be perpendicular to the substrate, or can be slightly flaring outward so the upper portion of the electrodes are wider than the lower portions, as illustrated in FIGS. 2 and 4. The upper portion of the electrode side walls could also be narrower than the lower portion (not shown).

In an alternative embodiment (not shown), the optical waveguides underlie the hot electrode even in the bend region, and reflective s-bends are not provided at the edges of the substrate. This embodiment, while having the advantage that etching can be performed between the electrodes without harming the optical waveguides, does not include compact turns, so requires more space on the substrate.

Modulators based on x-cut lithium niobate have typically been limited to a lower frequency range than modulators based on z-cut lithium niobate because for x-cut modulators the optical waveguides must go between the electrodes to utilize the larger electro-optic coefficient, r33. This limits the electrode gap width. Narrow gap widths require a shorter electrode height for velocity matching which in turn results in higher losses than experienced for the tall electrodes allowed for z-cut devices. As a result for x-cut devices there is a trade-off between higher drive voltage Vπ and frequency response. However, for applications in which the frequency range and drive voltage are not critical, the bridge electrode described herein can be included in x-cut lithium niobate based modulators. For such modulators, the lower portions of the bridge electrode can be arranged on either side of a waveguide, rather than directly aligned over the optical waveguide arms.

The following is a description of a suitable method for forming the electro-optic modulators of FIG. 1-5. A substrate is suitably selected as a z-cut optical-grade commercial lithium niobate wafer. The z plane is the plane perpendicular to the crystal axis (z) and is the largest face of the substrate. The wafer can be approximately 3-4 inches in diameter with a 1 mm thickness, although larger or smaller size wafers can be used. The wafer is cleaned in trichloroethylene, acetone, methanol, detergent, and deionized water. Titanium is sputtered at room temperature over the z face to a thickness of 600 angstroms. Optical waveguides can be formed in the substrate photolithographically by spin-coating photoresist on the substrate, prebaking the photoresist at 90 degrees C. for 25 minutes, exposing the photoresist to UV light through the optical waveguide photomask, with the optical waveguides aligned along the y-axis of the substrate. The photoresist is then developed to eliminate it, and postbaked at 110 degrees C. for 45 minutes to fully harden it in the optical waveguide regions. Finally, the titanium is etched away by the use of ethylene diamine tetraacetic acid (EDTA). The final titanium strip width after etching is 8 um and produces single-mode waveguides after indiffusion of titanium. The substrate is then placed in a furnace and heated to an elevated temperature of 1000 degrees C. for 10 hours in wet oxygen. This technique produces high quality optical waveguides with very low propagation losses in straight channels, for example, losses of approximately 0.1 dB/cm.

A poling mask is used to define a poling electrode over one of the two waveguide regions. A voltage is applied to the poling electrode to reverse the ferroelectric domains in only one of the two waveguides. The net effect of this poling is a reduction in modulator drive voltage. After reverse poling is completed, the poling electrode is chemically etched away. An etch mask is then used to define the areas on the substrate that are to be etched by ion milling or another suitable technique. The lithium niobate ridge (unetched area) can be slightly wider than the electrode footprint, for example, to minimize optical loss in the active region associated with roughness of the etched surface.

A buffer layer of silicon dioxide is deposited over the wafer after etching of the substrate. Alternatively, the buffer layer can be deposited prior to etching.

The layering process for the electrodes is illustrated by FIG. 4. A first modulator electrode mask is used to define the foundation (lower portion or legs) of the bridge electrode, and a first layer of the ground planes. The electrodes are plated everywhere to a height h1 of 20 microns. In a preferred embodiment, the electrodes are formed of gold. For structural support, the volume between the legs of the bridge electrode can be filled with a polymer or other suitable material before the upper layer is applied.

A second modulator mask is used to define the center hot electrode and all other electrodes, and the electrodes are plated to an additional height h2 of 10 microns. This completes the formation of the 30 micron electrode height in the turning region.

A third modulator mask is used to form the mold for the linear part of the modulator between the turns, where the hot electrode and the ground planes are plated with another 60 microns of electrode material (h3), for a total of 90 microns in height (in the z direction).

The input and output horns couple RF input energy to the first active region and from the last active region of the modulator. The input and output horns can have a thickness of approximately 20 microns. In this embodiment, the horns are not impedance matched. Their length is less than the wavelength of the RF energy, so impedance matching is not necessary. The impedance, effective refractive index, and gold thickness in microns of the FIG. 3-5 embodiment is as follows:

Z gold region (ohms) n eff thickness characteristics linear active 48 2.14 90 microns velocity and impedance region matched turns 48 3.41 30 microns impedance matched horns 38 2.6 20 microns not impedance matched (RF to active)

A significant advantage of the modulators described herein is that they are inherently chirp-free. For a Mach-Zehnder modulator, chirp is the ratio of the phase modulation to the amplitude modulation where the phase modulation is the time averaged phase modulation for both waveguides in the Mach-Zehnder modulator. Previous Mach-Zehnder modulators that apply different electrical fields to the two waveguide arms are susceptible to chirp due to the differential in the electric field applied to each electrode over the two waveguides. In MZMs with one electrode at ground potential (zero electrical field) and the other electrode at the maximum applied voltage, the optical waveguide under the grounded electrode has only a small contribution to the average phase while the other optical waveguide has most of the modulation phase shift.

In contrast, the electrode bridges configurations disclosed herein and illustrated in FIG. 1-5 allows the same electrical field to be applied to both waveguides. Therefore, the magnitude of the optical signal's phase shift is the same in each waveguide. Since one of the optical waveguides is reverse poled, the sign of the phase modulation in one of the optical waveguides is reversed relative to the other waveguide. This results in a time averaged phase modulation of zero for equal length waveguides. Thus, the bridge structure electrodes are inherently chirp-free.

Another advantage of the electrode configuration disclosed herein is that the fabrication tolerances for the bridge structure are reduced compared to coplanar waveguide structures. Although more masks are used to define the bridge structure, only the bottom electrode layer of 20 μm requires precise alignment during the photolithography stage. In contrast, other low-loss coplanar waveguides not having a bridge structure require thicker electrodes in a single step (e.g., greater than 40 microns), making the alignment during the photolithography process much more difficult.

For a number of modulator applications a modulator drive voltage of 0.5 V or less is desirable. Further, operation without a low noise amplifier between the electrical source (such as an antenna) and the modulator can be desirable due to a lack of electrical power locally, to minimize local power consumption, or to eliminate distortion products created by the nonlinearities of the amplifier. For example, with drive voltages of 0.5 V or less, microwave transmission from antennas can be accomplished without any amplifier at the antenna and with RF gain in the fiber optic link and noise figure of the same order as a low noise amplifier.

FIG. 6 and the following table illustrate the projected drive voltage for single pass and multi-pass modulators using the bridge electrode configuration described herein. The modulator illustrated in FIG. 3-5 having a low-loss bridge electrode structure, five active regions, and compact waveguide turns provides a Lithium niobate Mach-Zehnder modulator design with a projected drive voltage of 0.6 V or less through 20 GHz. The modulator illustrated in FIGS. 1-2 and 3-5 are projected to have a drive voltage of 1.4 V or less through 20 GHz.

Model at 1.55 Micron Optical Signal Wavelenght:

Vπ (Volts) Interaction Passes DC 10 GHz 20 GHz Length (cm) 1 1.2 1.33 1.4 7.4 3 0.4 0.55 0.67 23.4 5 0.2 0.4 0.57 39.4

Achieving the low drive voltage over the 0-20 GHz frequency range is very useful for applications where amplifiers cannot be used between the RF source and the modulator, particularly where weight, size, power dissipation and power consumption are issues. Further, by eliminating amplifiers in RF systems, the lack of amplifier noise and distortion generated by the inter-modulation products of the amplifier improves the sensitivity of the RF system. System applications include wing mounted antenna array telemetry, space based systems and commercial and military telecommunication systems in which significant cost savings can be achieved while increasing reliability. With drive voltages of less than 0.5 V, microwave signals from antennas can be received without any amplifier at the antenna and transmitted over optical fiber with RF gain in the link and noise figure of the same order as a low noise amplifier.

The modulators and electrodes of FIG. 1-5 are also suitable for modulation at frequencies greater than 20 GHz.

The following discussion is provided to clarify the advantages of providing a single electrode with reverse poled waveguides compared to other modulator types. Four possible configurations of a single pass modulator are as follows: (1) a hot electrode over one waveguide with no electrode over the other waveguide; (2) a hot electrode over one waveguide with a ground plane over the other waveguide; (3) a hot electrode over one waveguide with a second hot electrode over the other waveguide, operating with two electrical driving signals which are 180 degrees out of phase; and (4) a hot electrode over one waveguide with a second hot electrode over the other waveguide operating with either a single electrical signal or two electrical driving signals in phase, with the optical waveguide under one electrode being reverse poled to change the sign of the modulation.

Push-pull is a method of combining two signals that are out of phase to get more modulation effect between the two waveguides forming the Mach-Zehnder interferometer. The push pull method can be implemented through electrode or optical design. The electrode configurations of (3) and (4) are referred to as push-pull. Electrode designs consistent with configuration (2) can also provide a small increase in modulation efficiency compared with configuration (1) due to non-negligible field intensity under the ground electrode. It should also be noted that the push-pull configurations (3) and (4) are sometimes erroneously considered to provide twice the modulation due to the push-pull configuration. In the case of a RF source without amplification, the power must be divided between the two electrodes. Since these modulators respond to the voltage developed across the electrodes, the maximum improvement over configuration (1) modulators is 2^(1/2) for typical 50 ohm systems rather than a full factor of 2.

For applications where there is no amplifier between the RF driving source and the modulator, configurations (2) and (4) are the most promising. Configuration (1) has the poorest effective response of all configurations and configuration (3) requires a wideband power divider and a low-loss 180 degree RF phase shifter.

In order to maximize the modulator bandwidth and response, traveling wave modulator designs are employed or device length is shortened at the expense of increased drive voltage requirements. The modulators are designed such that the velocity of propagation of the optical wave is matched to the velocity of the microwave by adjusting the geometry of the electrode. For high frequency traveling wave modulators, as the active region length is increased to reduce the dc drive voltage, the impact of increased electrode losses becomes more significant, causing the response to deteriorate rapidly at high frequency. Therefore, in order to take advantage of increased active region length enabled by compact reflective turns, extremely low loss electrode structures are desired. The electrode designs described in this disclosure can provide losses which are lower than conventional structures, ultimately enabling less than 0.5 V drive voltages.

FIG. 7, a graph of electrode transmission versus frequency, illustrates that the bridge electrodes as illustrated in FIGS. 2 and 4 provide substantially reduced loss over other coplanar waveguide designs. Curves A show measured results for a single pass modulator with a 4.5 cm interaction length coplanar waveguide electrodes, a 25 micron gap, and a 32 micron height. Further details are provided in M. M. Howerton, R. P. Moeller, A. S. Greenblatt, and R. Krahenbuhl, “Fully packaged Broad-band LiNbO3 Modulator with Low Drive Voltage,”, IEEE Photon. Technol. Lett. 12, 792-794 (2000), and fitted loss coefficient of 0.043 (GHz ^(1/2)-cm)⁻¹ for this modulator. Curves B represent a modulator with improved coplanar waveguide electrode morphology, resulting in a loss coefficient of 0.025 (GHz ^(1/2)-cm)⁻¹. Curves C represent measured and curve fitted results for a modulator with a coplanar waveguide gap width of 45 microns and electrode height of approximately 45 microns. The loss coefficient for this modulator is α₀=0.015 (GHz ^(1/2)-cm)⁻¹. The height for this electrode was slightly short of that appropriate for velocity matching for the curve C modulator.

Curves D of FIG. 7 shows the electrical transmission for the bridge structure disclosed herein with a 90 micron electrode height in the active region, without etching between the lower portions of the active electrode, and without etching between the active electrode and the ground planes. The fitted curve D corresponds to a loss coefficient of 0.008 (GHz ^(1/2)-cm)⁻¹.

Further reductions in electrode losses of CPW structures are possible by increasing the electrode gap between the center electrode and the ground plane of coplanar waveguide electrodes and increasing the thickness of the electrode. Curve E represents the projected loss of an optimized bridge design with etching, calculated using a three dimensional finite element model. The projected loss coefficient is 0.0065 (GHz ^(1/2)-cm)⁻¹, which includes both resistive and dielectric contributions.

Thus, the bridge electrode design disclosed herein provides a substantial reduction in electrode loss compared to other coplanar waveguide designs shown in FIG. 7.

FIG. 8 illustrates the electrode loss versus electrode gap for coplanar waveguide structures. As the gap is increased, the electrode height should also be increased to ensure that the optical velocity and RF velocity are matched. FIG. 9 illustrates the electrode transmission versus frequency for coplanar waveguide structures. FIG. 10 illustrates the loss coefficient, dc drive voltage Vπ (DC) and 20 GHz drive voltage Vπ (20 GHz). As illustrated in FIGS. 9 and 10, drive voltages of less than 0.5 V at 20 GHz are not feasible for the configuration (2) coplanar waveguide.

As the modulators illustrated in FIG. 1-4 each have reverse-poled waveguide arms and a single hot electrode, they correspond best to the configuration (4) structure discussed in previous paragraphs. Thus, the FIG. 1-4 modulators provide significant advantages over coplanar waveguide structures.

FIG. 11 is an expanded view of the substrate and bridge structure of FIG. 2 or 4. FIG. 12 illustrates the first layer of metallization forming the base level of an active electrode 150 or 350 shown in FIG. 1-2 or 3-5. The active electrode 150 is spaced apart from each ground plane by 100 microns, and each of the electrode legs is 8 microns in width. The two optical waveguides should be separated enough to limit optical crosstalk. Deep ion etching as illustrated in FIG. 11 can limit crosstalk between the optical waveguides while minimizing the gap between the optical waveguides.

The upper portion of the active bridge electrode can extend in the width direction beyond the outer edges of the electrode base layer. A large surface area is preferred for decreasing the loss in the electrode.

FIG. 13A-B illustrate cross sectional views of an electro-optic phase modulator according to another embodiment of the invention. An optical waveguide 640 is formed in a substrate 660 by the titanium indiffusion method described above, or by another suitable method. An electrode 650 and ground plane 610 are formed on the substrate. The hot electrode is spaced apart from a ground plane 610. As seen in FIG. 13A, the electrode 650 has a lower portion 652 aligned with the optical waveguide 630 in a manner such that applying a RF signal to the electrode induces a change in the refractive index of the optical waveguide, in turn producing a velocity matched optical signal in the optical waveguide. The lower portion 652 preferably has a width about the same as the width of the optical waveguide. The upper portion 656 of the electrode is wider than the lower portion, and preferably is at least twice, and more preferably, at least three times as wide as the lower portion. For example, a presently preferred width for the upper portion of the electrode is 32 microns when the lower portion is 8 microns wide, with the electrode having a total height of 90 microns. A polymer or other suitable electrically insulative material can be deposited on the substrate in the areas 612 and 614 on either side of the lower portion of the electrode to provide a stable platform on which to deposit the subsequent layer or layers of the electrode.

As seen in FIG. 13B, the electrode can also have more than one lower portion to provide a stable base for the subsequently deposited layers of the electrode. In this embodiment, only one of the lower portions 652 will be aligned over the waveguide.

FIG. 14 is an expanded view of a bridge electrode 700. In this embodiment, the bridge electrode 700 has lower portions 710 and 720 arranged over parallel optical waveguides 730 and 740. A buffer layer is positioned between the electrode 700 and the Z-cut lithium niobate substrate 760.

The parallel optical waveguides 710 and 720 can be formed by titanium diffusion into the substrate. A groove can be etched in the substrate between the optical waveguides, with the groove being about the same width as the width of the waveguides 730 and 740. Grooves are also etched in the substrate between each waveguide and the ground planes 770 and 780. Etching grooves in the substrate around the waveguide can be advantageous for two advantages. First, the etching concentrates the induced field in the optical waveguide. The high dielectric constant of the waveguide material restricts the field from spreading out into the air in the surrounding etched region on either side of the waveguides.

In this embodiment, the unetched lithium niobate substrates in the waveguide regions are about 12 microns in width, and the electrode legs are about 8 microns in width. The width of the electrode upper portion is about 32 microns, and the overall electrode height is about 90 microns. The lower portions of the electrode have a width of about 8 microns.

The electrode 700 has an upper surface 750 that is the farthest point from the substrate top surface of the electrode 760. The corners 752 and 754 between the upper surface 750 and the side walls are sharp.

The electrode 700 can be formed by a process of gold plating the lower portions of the electrode and the upper portion of the electrode, in the manner discussed in preceding paragraphs addressing FIG. 4, or by any other suitable means.

FIG. 15 is a cross sectional view of a bridge electrode 800 in accordance with another embodiment of the invention. The substrate structure and waveguides are identical to those in FIG. 14. The top surface of the electrode 800 has rounded corners 811 and 812. Each corner 811, 812 has a radius of curvature of about ¼ to about ½ of the width of the electrode. In the embodiment shown in FIG. 15, the corners 811, 812 have a radius of curvature of 16 microns. The electrode width is about 38 microns, resulting in a flat upper surface 810 of about 6 microns.

The parallel lower portions 860 and 870 of the electrode each have rounded corners 862, 864 and 872, 874.

The contact area of the electrode legs should have a width that is about equal to the width of the optical waveguide. In this example, the rounded corners 862, 864, 872, 874 have a radius of curvature of about four microns, the width of the optical waveguide is about 8 microns, and the corresponding contact areas of the electrode legs are about 8 microns in width. The rounded corners of the electrode legs can have a radius of curvature of about half of the contact area width, although it can be greater or smaller. In this embodiment, the radius of curvature is about 4 microns, resulting in a width of each of the lower portions of about 16 microns.

The interior corners 882, 884 of the electrode 800 do not concentrate the electrical field, so it is not necessary to radius these corners to reduce loss. However, the corners 882, 884 can be curved if desired.

The curved exterior corners of the electrode are believed to result in an electrical field in the electrode that is less concentrated in the corner regions, reducing the electrical loss. The rounded corners of the lower portions of the electrode allows the overall width of the electrode to be wider, and the comparatively wider electrode 800 result in lower loss, compared to the electrode 700 of FIG. 14. These characteristics allow the FIG. 15 electro-optic modulator to have an electrical loss of about 0.2 decibels per centimeter, compared with the FIG. 14 electro-optic modulator's electrical loss of about 0.3 decibels per centimeter. The low-loss properties of the rounded corner bridge electrode allows an electro-optic modulator to operate at lower drive voltages.

The region between the electrode legs 860 and 870 and the ground planes 840 and 830 are etched, to concentrate the induced field in the optical waveguide and restrict the field from spreading out into the air in the surrounding etched region on either side of the waveguides.

A wider gap between the active electrode 800 and the ground electrodes 830 and 840 allows the electrodes to be taller, reducing the electrical loss. A gap of about 100 microns between the active electrode 800 and the ground electrodes 830 and 840 is appropriate for optical modulation at frequencies up to about 20 GHz. The gap can be wider for lower frequencies. For example, the gap can be between 150 and 200 microns for frequencies in the six to twelve gigahertz range.

Aspects of the invention also include methods for making the rounded corner electrodes described herein. An example of a method for manufacturing the rounded cornered bridge electrode of FIG. 15 is shown in FIG. 16A-M.

FIG. 16A illustrates the substrate 900, a buffer layer 902, a metal seed layer 904, and etched regions 906, 907, and 908. The titanium diffused waveguides (not shown) have been poled. It is preferred that the grooves are etched in the substrate before poling the electrodes, in order to minimize waste due to errors in the etching process, however, it is also possible to pole the electrodes before etching the grooves in the waveguides.

a) If using a positive photoresist, apply the photoresist 910 over the electrode region, as shown in FIG. 16B.

Next, expose the desired portion of the photoresist to light, using a mask 912 to prevent light from reaching the remaining portion of the photoresist, as illustrated in FIG. 16C. Use a solution to wash away or dissolve the exposed photoresist. FIG. 16D shows the resulting mold that remains after the exposed photoresist is removed. The mold has grooves 914, 916, 918, and 920 in which the electrodes will be formed.

FIGS. 16E, 16F, and 16G are expanded views of the active bridge electrode region. FIG. 16E illustrates application of a photoresist solution with sufficient viscosity to the grooves 916 and 918 to fill in the corners of the mold. Capillary action causes the liquid to form a concave surface in the corners 922, 924, 926, and 928. The photoresist solution is allowed to harden.

As shown in FIG. 16F, the liquid may cover the bottom of the mold. If so, another mask can be used to expose a narrower section of the electrode, and a solution can be used to wash away/dissolve the excess photoresist in the center of the electrode base, to expose the metal seed layer 904 and form the flat base 932 and 934 of the electrode.

What remains is a mold with grooves and rounded edges in which the electrodes will be formed.

As illustrated in FIG. 16H, a first layer of the electrodes are formed on the exposed metal seed layer in the mold by plating metallic electrode material into the grooves between the masks. The first layer of electrode material forms the lower portions 940 and 942 of the active bridge electrode and a first layer of the ground electrodes 936 and 938.

Repeat the steps of applying a photoresist, exposing portions of the photoresist to light, dissolving the exposed photoresist, and electroplating the metallic electrode material as necessary to build the electrodes to the desired height and to form the bridge structure.

For example, in FIG. 16I, a positive photoresist 944 has been applied over the electrode region, and portions of the photoresist are exposed to light, with other portions protected by a mask 946. In FIG. 16J, the exposed photoresist has been dissolved or washed away, forming grooves 948, 950, 952 in which the next layer of electrode will be formed. Metal electrode material 954, 956, and 958 is plated into the grooves to build the electrodes in height, as shown in FIG. 16K.

As seen in FIG. 16L, to form the rounded corners on the upper surface of the active electrode, progressively narrower layers of gold material are plated onto the center electrode.

As a final step, the electrode region is exposed to light, and a solution is used to dissolve the remaining photoresist, leaving the completed center electrode and ground electrodes in place, as illustrated in FIG. 16M.

Note that if the photoresist is negative, the process is similar, except that a mask is used to block light from reaching the areas intended to be dissolved, rather than the areas that will not be dissolved.

Rounded corner electrodes are not limited to the bridge electrode configuration of FIG. 16. FIG. 17 illustrates another embodiment of an electro-optic modulator having rounded corners on the electrode. FIG. 17 is a cross sectional view of the electrode portion of an electro-optic modulator with rounded upper and lower corners for the active electrode 970. Note that FIG. 17 is not to scale, and the distance between the active electrode and the ground electrodes 980 and 990 is larger than it appears. A plan view of the modulator shown in FIG. 17 is similar to the FIG. 1A or FIG. 1B in U.S. Pat. No. 5,416,859, incorporated by reference herein in its entirety.

The rounded corner electrode and electro-optic modulator of FIG. 17 are made in a manner similar to the method described for producing the bridge electrode of FIG. 15.

Obviously, many modifications and variations of the present invention are possible in light of the above teachings. It is therefore to be understood that the claimed invention may be practiced otherwise than as specifically described. 

1. An electro-optic modulator comprising: a substrate having at least one optical waveguide formed on a face of the substrate; at least one active electrode formed on the first face of the substrate and aligned over the optical waveguide; the active electrode operating to induce a refractive index change in the optical waveguide, the active electrode having a lower surface arranged facing the substrate, an upper surface arranged away from the substrate, and substantially planar side walls extending between the lower and upper surfaces, wherein the active electrode has convex rounded corners between the side walls and the lower surface of the active electrode.
 2. The electro-optic modulator of claim 1, wherein the radius of curvature of the rounded corners is between about 25% and 75% of the width of the contact area of the electrode.
 3. The electro-optic modulator of claim 1, wherein the substrate comprises Z-cut lithium niobate.
 4. The electro-optic modulator of claim 3, wherein the substrate further comprises a silicon dioxide buffer layer.
 5. The electro-optic modulator of claim 1, wherein the substrate further comprises a metal seed layer arranged over the silicon dioxide buffer layer.
 6. The electro-optic modulator of claim 1, wherein the radius of curvature of the rounded corners is between about half of the width of the contact area between the active electrode and the substrate.
 7. The electro-optic modulator of claim 1, wherein the width of the contact area between the active electrode and the substrate is about half of the maximum width of the active electrode.
 8. The electro-optic modulator of claim 1, wherein the upper surface of the active electrode is convex.
 9. The electro-optic modulator of claim 1, wherein the active electrode has rounded corners between the side walls and the upper surface.
 10. The electro-optic modulator according to claim 9, wherein the radius of curvature of the upper surface corners is between about ¼ and ½ of the maximum width of the active electrode.
 11. An electro-optic modulator comprising: a substrate having at least one optical waveguide formed on a face of the substrate; and at least one active electrode formed on the first face of the substrate aligned over the optical waveguide and operable to induce a refractive index change in the optical waveguide; the active electrode having a wider upper portion and at least two narrower lower portions, each of the narrower lower portions being arranged between the wider upper portion and the optical waveguide, the narrower portions having a surface arranged facing the substrate, the wider upper portion having an upper surface arranged away from the substrate, and the active electrode having substantially planar side walls extending between the lower and upper surfaces of the electrode, wherein each of the narrower lower portions of the active electrode has convex rounded corners between the side walls and the lower surface of the active electrode.
 12. An electro-optic modulator according to claim 11, the wider upper portion joining the two narrower lower portions and extending over the two parallel optical waveguides, the narrower lower portions being arranged between the wider upper portion and the substrate.
 13. The electro-optic modulator of claim 11, wherein the radius of curvature of each of the rounded corners is between about 25% and 75% of the width of the contact area of the electrode.
 14. The electro-optic modulator of claim 11, wherein the radius of curvature of each of the rounded corners is about half of the width of the contact area of the active electrode.
 15. The electro-optic modulator of claim 11, wherein the width of the contact area of the active electrode is less than half of the maximum width of the active electrode.
 16. The electro-optic modulator of claim 11, wherein the upper surface of the active electrode is convex.
 17. The electro-optic modulator of claim 11, wherein the width of the each of the narrower lower portions is about eight microns.
 18. The electro-optic modulator of claim 11, wherein each of the narrower lower portions of the active electrode overlie a different one of the optical waveguides in an active region of the modulator.
 19. The electro-optic modulator according to claim 11, further comprising: at least one ground plane formed on the first face of the substrate spaced apart from the active electrode.
 20. The electro-optic modulator of claim 19, wherein the at least one ground plane comprises a first ground plane on one side of the active electrode and a second ground plane arranged on a side of the active electrode opposite the first ground plane.
 21. The electro-optic modulator according to claim 11, further comprising: ground planes formed on opposite sides of the active electrode, spaced apart from the active electrode.
 22. The electro-optic modulator of claim 11, further comprising at least one groove in the substrate between the optical waveguides.
 23. The electro-optic modulator of claim 11, further comprising at least one groove in the substrate between the active electrode and the ground plane.
 24. The electro-optic modulator according to claim 11, wherein the modulator is a Mach-Zehnder modulator. 